Data path differentiator for pre-emphasis requirement or slot identification

ABSTRACT

An apparatus and method is disclosed for generating path length information for two (usually redundant) receive paths in a receiving device such as a server blade so that the proper amount of equalization and/or pre-emphasis may be applied to receiver and driver circuits in the server blade. In one embodiment, the path length information comprises a longer or shorter path determination, and may also include a estimation of the slot location. In another embodiment, the path length information comprises a representation of the length of two receive paths. The path length information generating circuit is connected to the two receive inputs of the receiving device though high impedance elements, and the path length information may be utilized by hardware or a processor to set the equalization or pre-emphasis in the receiver and/or driver.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No.11/369,326, filed Mar. 6, 2006, the entire disclosure of which isincorporated herein by reference in its entirety for all purposes.

FIELD OF THE INVENTION

This invention relates to communications between devices within bladeservers, and more particularly in one embodiment, to an apparatus forautomatically identifying and/or estimating the lengths of data pathsbetween redundant interface devices and one or more Input/OutputControllers (IOCs) within the blade server to assist in equalizing thefrequency response of those data paths.

BACKGROUND OF THE INVENTION

FIG. 1 is an illustration of an exemplary conventional blade server 100connected to an external switched fabric 108. Blade servers overcomesome of the inefficiencies of individual standalone or rack-mounted OneUnit (1U) high servers, each of which is self-contained and includesseparate power supplies, fans, and the like, and are thereforeinefficient in terms of space, power, cooling, and othercharacteristics. Blade servers 100 utilize a modular, plug-in approachwherein the housing for each server is eliminated along withself-contained components such as power supplies and fans. Eachpreviously standalone server is therefore reduced to a server “blade”102 capable of being plugged into a backplane or midplane 104 within theblade server chassis 106 from the front of the chassis. Typically, twoto 14 blades may be installed in a single blade server chassis 106. Themidplane 104 contains connectors for receiving the server blades 102 andtypically contains from one to four “lanes” or paths on a PrintedCircuit Board (PCB) for carrying high-speed data signals. The midplane104 therefore eliminates much of the cabling that was required withindividual servers. The blade server chassis 106 also provides redundantcommon cooling and power to the server blades 102 through the midplane104.

Conventional blade servers 100 may be connected to redundant externalswitch fabrics 108 through interface cards such as an “A” sideInput/Output (I/O) switch 110 and a “B” side I/O switch 112, which pluginto the midplane 104 from the back of the chassis 106. Typically, theredundancy enables one switch to take over if the other fails.Alternatively, in Switched Bunch Of Disk (SBOD) or Just a Bunch Of Disks(JBOD) implementations, a blade server may comprise multiple disk drivescontained in SBODs or JBODs connected to the backplane through aninterface card without a connection to the network, instead of the I/Oswitches 110 and 112 shown in FIG. 1. In a typical SBOD, the serverblades 102 have an I/O port directly on them, and talk to the drivesover the midplane.

The blade server midplane 104 is typically rooted/designed to allow forone or more independent redundant fabrics or I/O protocols, such asFibre Channel (FC), Ethernet or InfiniBand. In the case of a FCconfiguration, each embedded switch 110 and 112 may be a FC ArbitratedLoop (FC_AL) switch or a full fabric switch, with a separate port toconnect to each of the multiple server blades 102 (but shown connectedto only one server blade 102 in FIG. 1) over a FC link 116 or 118, andoutput ports for connecting to the external switched fabrics 108.

To enable the server blades 102 to communicate with the switch fabric, amezzanine I/O card 114 that performs a Host Bus Adapter (HBA) (a.k.a.IOC) function is typically required in each server blade 102. Thesemezzanine I/O cards 114 may be mounted to the server blades 102 asdaughter cards. Alternatively, an IOC may be mounted directly on theserver blade. For purposes of this specification, mezzanine I/O cards114, referred to herein, include both daughter cards and IOCs mounteddirectly onto the server blade. The connections to the mezzanine I/Ocard 114 include the two I/O links 116 and 118 routed from each of thetwo embedded switches 110 and 112 through the midplane 104. Themezzanine I/O cards 114 follow the standard device driver model, so thatwhen a server blade 102 with a mezzanine I/O card 114 is plugged intothe midplane 104 and connected to an embedded switch 110 or 112, itappears to be a standalone server communicating with an external switch.Note that switches 110 and 112 in FIG. 1 may alternatively be replacedwith “pass-through” transceiver cards.

Depending on where the I/O switches 110 and 112 are plugged into themidplane 104, and where the server blades 102 are plugged into themidplane, the redundant data paths 116 and 118 may be drasticallydifferent in length, very similar in length, or anywhere in between.Given the conventional implementation of a blade server 100 asillustrated in FIG. 1, or alternatively in SBOD or JBOD implementationsor any backplane/midplane system with redundant data paths, thedifferent lengths will cause each of the two redundant data paths 116and 118 to have different and distinguishable losses at all frequencies,provided impedance matching of the system is maintained to a reasonabledegree. These differences may cause transmission errors and unacceptableerror rates, among other things.

In some legacy blade servers, the driver circuitry generates the bestsignal possible, and the receiver circuitry simply receives thetransmitted signals with differences in attenuation, however large orsmall, as influenced by the path lengths. However, because frequenciesand data rates have increased, resulting in higher signal attenuation,especially at the upper (higher) frequencies of the data signal (andhence more deterministic jitter), conventional modern systems may employtransmitter circuits with pre-emphasis on their transmit outputs in anattempt to transmit data with an enhanced frequency response in order toreceive a flat frequency response at the far or “receiving” end, andachieve acceptable bit error rates.

Referring to FIG. 2, a standard amplifier 200 in a transmitter circuitgenerates an output “eye” diagram 202 in the time domain. At lowerfrequencies, the transmit signal peak-to-peak amplitude may besubstantial as indicated at 204, but at higher frequencies, the transmitsignal peak-to-peak amplitude may be less substantial as indicated at206, and the eye will get progressively smaller. In the frequencydomain, the higher frequencies taper off in amplitude, as indicated at208. Given a 4.250 Gbit/sec signal, at 2125 MHz the amplitude may taperoff by 6 dB, half the original voltage or more. Because of the rolloffof the amplifier at high frequencies, the eye in the time domain closesat those frequencies, and data can no longer be accurately transmittedwith acceptable error rates, if at all.

To compensate for this frequency domain rolloff, programmablepre-emphasis circuitry can be added to the amplifiers to give theamplifier an equivalent boost at the higher frequencies. For example,firmware and registers can be employed to control the amount of boost(de-emphasis) by communicating a 3-bit word (e.g. 000 to 111) 210 topre-emphasis circuitry 212 within the amplifier, which iswell-understood by those skilled in the art. The pre-emphasis circuitry212 is adjustable and provides internal compensation to compensate forthe path so that the frequency response at the receiving end becomesrelatively flat over all frequencies (see reference character 214),which is desirable. However, even though the true definition ofpre-emphasis is boosting of the higher frequencies, the transmitamplifier is limited by its supply voltages. For example, if thetransmit amplifier is supplied by a 3 volt rail, the eye cannot be morethan 3 volts high (at which point “rail-out” occurs), and thus even withpre-emphasis the output amplitude cannot be more than 3 volts.Therefore, rather than boost the higher frequencies to above 3 volts,which is not possible, pre-emphasis circuitry actually maximizes theoutput at the upper frequencies (e.g. 2125 MHz) towards the upper rail(e.g. +3V), and de-emphasizes the lower frequencies to create therelatively flat frequency response. Depending on the bandwidth of theamplifier, the amplitude of the resultant eye will roughly correspond tothe amplitude at which the rolloff occurs after equalization.

Alternatively or in addition to transmit circuit pre-emphasis,conventional modern systems may also have IOC integrated circuits withequalizers on their receiver inputs, or equalizer circuits external toand ahead of the IOC integrated circuits, to customize the frequencyresponse for a particular path and equalize the redundant data paths sothat they have approximately the same frequency response over a givenfrequency range.

Referring now to FIG. 3, at the transmitter end 300 pre-emphasis 314 maybe used as described above to de-emphasize the lower frequencies (seereference character 302) to flatten out the frequency response as seenat the receiving end. However, after the signal passes through thetransmission lines 306 in the midplane of the blade server, rolloff (seereference character 308) once again occurs at the higher frequencies atthe receive end 310, and the signal level may be much lower (e.g. 250 mVpeak to peak), which is not near any rail. If the transmitter cannotpre-emphasize enough to substantially reduce receive end rolloff,equalization 316 may be applied to the receive end to boost the higherfrequencies with gain to raise the signal level of all frequencies, andflatten out the frequency response (see reference character 312) to somepredetermined level acceptable to the receive end circuitry (e.g. 600 mVpeak to peak).

Ideally, the amount of equalization and/or pre-emphasis applied to eachtransmit amplifier or receiver would be customized for the length of thepath. Some modern conventional midplanes and devices do have some formof slot identification or path length determination built into theirhardware. Slot identification typically requires either dedicated pinson interface connectors or semiconductors (such as Electrically ErasableProgrammable Read Only Memories (EEPROMs)) to be designed into theoriginal Backplane/Midplane.

However, in order to save on costs, companies also desire to re-useprevious designs whenever possible, especially backplanes and midplanesalready in service at customer sites that do not have slotidentification. Without slot identification, it is difficult todetermine the proper pre-emphasis and/or equalization settings for thepath loss (link budget) at the faster data rates. Too much pre-emphasisor equalization will have the same effect as too little pre-emphasis orequalization, resulting in a higher bit error rate and less thanoptimized performance. Therefore, when a device such as a server bladeis plugged into the midplane, either human assessment and interventionis required to determine the slot location, approximate the pathlengths, and apply a custom amount of pre-emphasis and/or equalizationto the transmit and receive circuits, or alternatively, a fixed“compromise” amount of pre-emphasis and/or equalization for an averagepath length is applied that hopefully works for both paths regardless ofwhere the device is plugged into the midplane. The former approach isoften not practical, and the latter approach may result in some slotshaving overdriven signals and others having underdriven signals,resulting in unacceptable error rates and the need for complicated gaincontrol circuitry.

Therefore, there is a need to automatically identify and/or estimate thelengths of data paths between redundant interface devices and one ormore IOCs within the blade server to assist in equalizing the frequencyresponse of those data paths, without requiring dedicated pins oninterface connectors or semiconductors designed into the midplane.

SUMMARY OF THE INVENTION

Embodiments of the present invention are directed to an apparatus andmethod for generating path length information for two (usuallyredundant) receive paths in a receiving device such as a server blade sothat the proper amount of equalization and/or pre-emphasis may beapplied to receiver and driver circuits in the server blade. In oneembodiment, the path length information comprises a longer or shorterpath determination, and may also include a estimation of the slotlocation. In another embodiment, the path length information comprises arepresentation of the length of receive paths. The path lengthinformation generating circuit is connected to the two receive inputs ofthe receiving device though high impedance elements, and the path lengthinformation may be utilized by hardware or a processor to set theequalization or pre-emphasis in the receiver and/or driver.

Embodiments of the present invention assume that the driver circuits ineach of two redundant transmitting devices contain the same drivercircuitry or adhere to the same standard for voltage output levels, suchthat the driving voltages should be within some reasonable range of eachother. The driver outputs from the two transmitting devices travel ashorter path and a longer path within a midplane or backplane, where,due to copper and dielectric losses in the transmission lines, thefrequencies in the long path are more highly attenuated than thefrequencies in the short path.

When the transmission lines for these two paths enter the receivingdevice, they are routed to a receiver, typically aSERializer/DESerializer (SERDES). Near the receiving device, thetransmission lines are sampled differentially by high impedanceelements.

In the embodiment mentioned above in which the path length informationgenerating circuit will give an indication as to whether the receivingdevice is inserted near the center of the midplane (or any location inthe range of slot locations as identified by a threshold value) andwhich paths are the longer and shorter paths, the high impedanceelements feed a differential amplifier for each data path to bring thesignal to a usable level and to convert it into a single ended signal,thereby simplifying and reducing requirements for further stages. Theseamplifiers will typically have the same gain or amplification level.

Once amplified, the signals are fed into filters, which may be high passfilters or bandpass filters, depending on the data encoding and the highfrequency components of the data being received. At high frequencies,where the long paths have significant loss as compared to the shortpaths, it is easier to compare the two paths. Thus, the filters may bebandpass filters that only pass frequencies at a selected highfrequency.

The energy at those frequencies will pass through the filters and chargeup envelope detectors. The output of the envelope detectors is a DCvoltage equivalent to the peak value of the amplitude of the datafrequency component desired. At this point, the path with the largestloss (the long path) will have significantly less voltage amplitude thanthe short path.

The two peak voltages from each of the envelope detectors are fed into acomparator, whose output provides an indication of which of the paths isthe most highly attenuated, and therefore, which is the longer path. Inparticular, if the output of the comparator is a high voltage, the pathconnected to the + input of the comparator is the shorter path, and ifthe output is a low voltage, the path connected to the − input of thecomparator is the shorter path.

To provide a better estimation of actual path lengths, the outputs ofthe envelope detectors can also be fed into a differential amplifier toamplify and scale the difference in the paths. If the receiving deviceis in a slot near the end of the midplane, the two paths are more likelyto be significantly different in length, and the output of thedifferential amplifier is more likely to be large as compared to whenthe receiving device is inserted into a middle slot and the paths aremore likely to be closer in length.

Setting a threshold on a second comparator and comparing it to theoutput of the differential amplifier can also provide an indication ofthe location of the receiving device as compared to the locationrepresented by the threshold.

Once the longer and shorter path determination and the relative positiondetermination has been made, this information may be converted to adigital value using an Analog to Digital (A/D) converter and can be usedby hardware and/or a processor to set pre-emphasis settings fortransmitters in the return paths of the receiving device (which may bethe same as the receive path lengths), and/or equalizer settings for thereceive path equalizers. Alternatively, instead of providing therelative position determination (output of the second comparator) to thehardware or processor, the output of the differential amplifier may beconverted using an A/D converter and provided to the hardware orprocessor for making the relative position determination andpre-emphasis settings. This embodiment does not enable perfectequalization/pre-emphasis, but provides an approximate indication ofwhere the receiving device is plugged into the midplane so the hardwareand/or processor can set the equalization with some level ofintelligence.

In the embodiment mentioned above in which the path length informationcomprises a representation of the length of receive paths, slotidentification circuitry is disclosed that takes advantage of the factthat interface boards such as I/O switches are plugged into fixedpositions in the midplane and connect to receiving devices such ascontroller cards or server blades via known fixed-length paths. Becausethe path length information is known, a path length or slot positionindicator can be sent to the receiving devices in the form of a uniquecommon mode DC voltage across the FC (or other high speed serialinterface) transmission lines, allowing that device to know its pathlength or slot location so that it can determine pre-emphasis and orequalizations settings best suited for that path.

In this second embodiment, after the signals are sampled differentiallyby high impedance elements, the sampled signals are fed into low passfilters. The output of each filter is the applied common mode DC voltagerepresenting the length of that particular path. The DC voltages may beconverted to digital values using A/D converters and can be used byhardware and/or a processor to set pre-emphasis settings fortransmitters in the return paths of the receiving device and/orequalizer settings for the receive path equalizers.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is an illustration of an exemplary conventional blade serverconnected to an external switched fabric.

FIG. 2 is an illustration of an exemplary amplifier in a transmittercircuit and its corresponding output “eye” diagram in the time domainand rolloff in the frequency domain.

FIG. 3 is an illustration of an exemplary transmit amplifier and itscompensated frequency response using pre-emphasis and an exemplaryreceive amplifier and its compensated frequency response usingequalization.

FIG. 4 is an illustration of an exemplary blade server with a mezzanineI/O card employing a path length and slot estimation circuit accordingto embodiments of the present invention.

FIG. 5 is an illustration of an exemplary receiver and its rolled-offfrequency response and a bandpass filter at the higher frequencies foruse in determining path length and slot estimation according toembodiments of the present invention.

FIG. 6 is an illustration of an exemplary receiver and its rolled-offfrequency response and bandpass filters at various frequencies for usein determining the actual frequency response and the proper equalizationsetting according to embodiments of the present invention.

FIG. 7 is an illustration of an exemplary blade server and I/O switchesemploying a path identification circuit according to embodiments of thepresent invention.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT

In the following description of preferred embodiments, reference is madeto the accompanying drawings which form a part hereof, and in which itis shown by way of illustration specific embodiments in which theinvention may be practiced. It is to be understood that otherembodiments may be utilized and structural changes may be made withoutdeparting from the scope of the preferred embodiments of the presentinvention.

Although embodiments of the present invention may be described hereinprimarily in terms of FC signaling, it should be understood that thepresent invention is not limited to FC, but includes InfiniBand,Ethernet, Serial Attached Small Computer System Interconnect (SAS),Serial ATA (SATA) signaling and the like. Implementation of theseprotocols requires that the midplane support the protocol.

FIG. 4 is an illustration of an exemplary blade server 400 with multipleserver blades 402, each server blade including a controller, hostinterface card, HBA, or IOC, and each server blade employing a pathlength and slot estimation circuit according to embodiments of thepresent invention. However, it should be understood that embodiments ofthe present invention are generally applicable to any system comprisingtwo transmitting devices that transmit signals over a longer path and ashorter path to a receiving device. In the example of FIG. 4, serverblades 402, an interface card such as an “A” side I/O switch 410 and a“B” side I/O switch 412 are plugged into a midplane 404 within a bladeserver chassis. It should be understood that in SBOD or JBODimplementations, a blade server may comprise multiple disk drivesinstead of the multiple server blades 402 shown in FIG. 4.

To enable the server blades 402 to communicate with a switch fabricthrough the redundant I/O switches 410 and 412, a mezzanine I/O card 414that performs an HBA (a.k.a. IOC) function may be employed in eachserver blade 402. The connections to the mezzanine I/O card 414 includetwo differential I/O links (transmission lines) 416 and 418 routed fromeach of the two redundant I/O switches 410 and 412 through the midplane404. Note that although only the mezzanine I/O card receive paths 416and 418 are illustrated in FIG. 4 for simplicity, the mezzanine I/O card414 may also include drivers 446 and transmit paths (not shown) forsending signals to the redundant I/O switches 410 and 412. In addition,although FIG. 4 illustrates differential signals, embodiments of thepresent invention are also applicable to single-ended signals.

In the example of FIG. 4, redundant I/O switches 410 and 412 contain thesame driver circuitry or adhere to the same standard for voltage outputlevels, such that the driving voltages are within some reasonable rangeof each other. The driver outputs from each I/O switch 410 and 412travel the short path 416 and the long path 418, respectively, where,due to copper and dielectric losses, the frequencies in the long pathare more highly attenuated (e.g. 10 dB loss) than the frequencies in theshort path (e.g. 2 dB loss). More importantly, the higher frequencycomponents of the data signal will be attenuated the most, causing amuch larger difference in attenuation between the short and long pathsthan at the lower frequencies where both copper and dielectric lossesare small. After the transmission lines 416 and 418 for these two pathsenter the mezzanine I/O card 414 on the server blade 402, they arerouted to a receiving circuit, typically a SERializer/DESerializer(SERDES) 420.

The path length and slot estimation circuit according to embodiments ofthe present invention is shown surrounding the SERDES 420 in the exampleof FIG. 4. Although the path length and slot estimation circuit is shownin FIG. 4 within the mezzanine I/O card 414, it may be located in otherlocations on the server blade 402 or receiving device. The path lengthand slot estimation circuit will give an indication as to whether thereceiving device (e.g. server blade 402) is inserted near the center ofthe midplane 404 (or any location in the range of slot locations asidentified by a threshold value) and which paths are the longer andshorter paths. With this information, other hardware 422 or a processor424 operating under the control of firmware may control an equalizationcircuit in the receivers 448, well-understood by those skilled in theart, to flatten out the frequency response of the received signals. Theequalization may be built into the receiver 448 in the SERDES 420, asshown in FIG. 4, or may be external to the SERDES.

Near the receiver 420 (how near depends on the data rate and frequenciesinvolved) the transmission lines 416 and 418 are sampled differentiallyby high impedance elements 426. Note that the high impedance elements426 must be placed before the equalization circuitry 448. These highimpedance elements 426 are high enough impedance as compared to theimpedance of the transmission lines 416 and 418 (on the order of 10× ormore) so as to sample the data stream, but not disturb the data beingreceived.

The high impedance elements 426 feed a differential amplifier 428 (inthe case of differential signals) for each data path to bring the signalto a usable level and to convert it into a single ended signal, therebysimplifying and reducing requirements for further stages. Theseamplifiers 428 will typically have the same gain or amplification level.If the redundant data paths are single-ended, a differential amplifieris not needed, and if the signal levels are high enough, no amplifiermay be needed. FIG. 5 illustrates the frequency response 500 of the longtransmission line path 418 of FIG. 4 after amplification by amplifier428. Note that in FC embodiments, at high frequencies around 2125 MHz,the amplitude has dropped by 6 dB (could be 0 dB to 14 dB, typically).

Referring again to FIG. 4, once amplified, the signal is fed into afilter 430, which may be a high pass filter or bandpass filterwell-understood by those skilled in the art, depending on the dataencoding and the high frequency components of the data being received.The filter 430 can be comprised of discrete components or implemented ona printed circuit board using microwave filter techniques in order tokeep the cost of the implementation low.

The design of the filter 430 may be dependent on the communicationprotocol. For example, the FC protocol allows only up to five zeroes ina row before a one must be inserted, or up to five ones in a row beforea zero must be inserted. This requirement establishes the lowestfrequency that will be transmitted, which happens to be around 425 MHz.On the other hand, if every bit was toggled, the highest data frequencyof 2125 MHz would result. Thus, all permissible data patterns with havea frequency between these two ranges, not including sidebands.

As noted above, the amplitude differences are greatest at the highfrequencies. For example, if two disk drives are powered by a 3V rail,the best amplitude that could be expected at 2125 MHz may be about 2.7V.If one of the transmission line paths is short, the signal may drop byonly 1 dB (e.g. to 2.5V), while a long transmission line path may dropby 12 dB (e.g. to 0.7V). Therefore, at high frequencies, where the longpaths have significant loss as compared to the short paths, it is easierto compare the two paths. Thus, in a FC embodiment, the filter 430 maybe a bandpass filter that only passes frequencies at around 2125 MHz.Referring again to FIG. 5, the effect of this filter is to have abandpass region 502 around 2125 MHz.

Referring again to FIG. 4, as data flows through the transmission lines416 and 418, certain patterns will generate frequencies at 2125 MHz thatpass through filter 430. The energy at those frequencies will charge upan envelope detector 432 within a path length determination circuit 450.In the example of FIG. 4, the envelope detector 432 is comprised of arectifier in series with the signal and an integrator capacitor shuntedto ground. However, other designs well-understood to those skilled inthe art are possible. Note, however, that the envelope detector designmust allow an element such as a capacitor to charge up and hold itscharge during continuous monitoring, to determine the peak envelope(amplitude of the voltage). The output of the envelope detectors 432 isa DC voltage equivalent to the peak value of the amplitude of the datafrequency component desired. At this point, the path with the largestloss (the long path) will have significantly less voltage amplitude thatthe short path.

The two peak voltages from each of the envelope detectors 432 are fedinto comparator 434 within the path length determination circuit 450,whose output provides an indication of which of the paths is the mosthighly attenuated, and therefore, which is the longer path. Inparticular, if the output of the comparator is a high voltage, theshorter path is transmission line 416 (and the longer path istransmission line 418), and if the output is a low voltage, the shorterpath is transmission line 418 (and the longer path is transmission line416). It should be noted, however, that the longer and shorter pathdeterminations are only relative to each other, and do not provide anyindication of actual length. For example, if the server blade 402 isplugged into an end slot on the midplane 404, the difference in lengthbetween the two transmission lines 416 and 418 may be large, and clearlyone path is long compared to the other. However, if the server blade 402is plugged into a middle slot on the midplane 404, the difference inlength between the two transmission lines 416 and 418 may be small, yetone medium length path will be considered the longer path and the otherwill be considered the shorter path. Furthermore, depending on thelocations of the I/O switches 410 and 412, the two transmission lines416 and 418 may both be very short and nearly identical in length, yetone will be considered to be the longer path. Conversely, the twotransmission lines 416 and 418 may both be very long and nearlyidentical in length, yet one will be considered to be the shorter path.

To provide a better estimation of actual path lengths, the outputs ofthe envelope detectors 432 can also be fed into a differential amplifier436 to amplify and scale the difference in the paths. If the serverblade 402 is in a slot near the end of the midplane 404, the two pathsare more likely to be significantly different in length, and the outputof the differential amplifier 436 is more likely to be large as comparedto when the server blade 402 is inserted into a middle slot and thepaths are more likely to be closer in length.

Setting a threshold 438 on a second comparator 440 and comparing it tothe output of the differential amplifier 436 can also provide anindication of the location of the receiving device as compared to thelocation represented by the threshold. For example, a receiving devicelocated near an end of the midplane 404 may have large path lengthdifferences that shows up as a large voltage (e.g. 3V) on the output ofthe differential amplifier 436, a receiving device located near themiddle of the midplane may have small path length differences that showsup as a small voltage (e.g. 0.3V) on the output of the differentialamplifier, and a receiving device located halfway between the end andthe middle of the midplane (a “quarter” location) may have medium pathlength differences that shows up as a medium voltage (e.g. 1.5V) on theoutput of the differential amplifier. The threshold 438 can be set inadvance to any of these voltages to represent any of these slotlocations. When the comparator 440 compares the threshold 438 to theoutput of the differential amplifier, the slot location of the receivingdevice can be approximated. For example, if the threshold 438 is set to1.5V (representing the “quarter” location) and connected to the − inputof the comparator 440, and the output of the differential amplifier 436is connected to the + input of the comparator, then if the output of thecomparator is high, this is an indication that the receiving device islocated nearer to the end of the midplane than the “quarter” location.

Once the longer and shorter path determination and the relative positiondetermination has been made, this information may be converted to adigital value using A/D converters 454 and can be used by hardware 422and/or processor 424 to set pre-emphasis settings fordrivers/transmitters 446 in the return paths (which are typicallyapproximately the same as the receive path lengths), and/or equalizersettings for the receivers 448. For example, the digital valuesgenerated by the A/D converters 454 may cause the hardware 422 and/orprocessor 424 to set the receive circuit equalization 448 to one of 16different values. In an alternative embodiment, the digital values maydirectly toggle certain bits that program an equalizer to provide moreor less boost. In another alternative embodiment, these measurementscould be taken once, at startup, and the pre-emphasis or equalizationmanually set at that point. In yet another alternative embodiment,instead of using the second comparator 440 to provide a relativeposition determination, the output of the differential amplifier 436 maybe converted to a digital value using an A/D converter 454 and providedto the hardware or processor for making the relative positiondetermination and pre-emphasis settings. Embodiments of the presentinvention do not enable perfect equalization/pre-emphasis, but it atleast provides a rough indication of where the server blade 402 isplugged into the midplane 404 so the hardware 422 and/or processor 424can set the equalization/pre-emphasis with some level of intelligence.

Referring now to FIG. 6, which illustrates the frequency response of thelong transmission line path 418 of FIG. 4 after amplification byamplifier 428, note that the frequency responses is different atdifferent frequencies (e.g. 2125 MHz, 1063 MHz, 708 MHz, and 425 MHz).In an alternative embodiment of the present invention, a bandpass filtercould be employed at a set of different frequencies along with anenvelope detector to determine the amplitude at each of thesefrequencies. With this information, it is possible to determine the bestequalization (e.g. which one of 16 possible settings) is needed to mostclosely compensate for the rolloff and make it flat.

Embodiments of the present invention described above are directed to apath length and slot estimation circuit for use where no slotidentification circuitry is present. In alternative embodiments of thepresent invention described below, slot identification circuitry isdisclosed that takes advantage of the fact that interface boards such asI/O switches are plugged into fixed positions in the midplane andconnect to receiving devices such as controller cards or server bladesvia known fixed-length paths. Because the path length information isknown, a path length or slot position indicator can be sent to thereceiving devices via a unique common mode DC voltage across the FC (orother interface) transmission lines, allowing that device to know itspath length or slot location so that it can determine pre-emphasis andor equalizations settings best suited for that path.

It should be understood that “in-band” communications (data streamsadded to faster data streams, using lower frequencies than the systemPhase-Locked Loops (PLLs) can track) have been used in manyapplications. While the information in this alternative embodiment istraveling along a shared transmission line, there is no data streaminvolved as the information is a DC level (zero frequency, requiring DCblocks on the transmission lines) and it travels the lines in commonmode, making interference with the FC data signal literallynon-existent.

FIG. 7 is an illustration of an exemplary blade server 700 with I/Oswitch A 710 and I/O switch B 712 and multiple server blades 702(although only one is shown in FIG. 7), each I/O switch and server bladeemploying slot identification circuitry according to embodiments of thepresent invention. However, it should be understood that embodiments ofthe present invention are generally applicable to any system comprisingtwo transmitting devices that transmit signals over a longer path and ashorter path to a receiving device. In the example of FIG. 7, the serverblades 702, the “A” side I/O switch 710 and the “B” side I/O switch 712are plugged into a midplane 704 within a blade server chassis. It shouldbe understood that in SBOD or JBOD implementations, a blade server maycomprise multiple disk drives instead of the multiple server blades 702shown in FIG. 7, and would more properly be referred to as an SBOD orJBOD.

To enable the server blades 702 to communicate with a switch fabricthrough the redundant I/O switches 710 and 712, a mezzanine I/O card 714that performs an HBA (a.k.a. IOC) function may be employed in eachserver blade 702. The connections to the mezzanine I/O card 714 includetwo differential I/O links (transmission lines) 716 and 718 routed fromeach of the two redundant I/O switches 710 and 712 through the midplane704. Note that although only the mezzanine I/O card receive paths areillustrated in FIG. 7 for simplicity, the mezzanine I/O card 714 alsoincludes drivers 782 for sending signals to the redundant I/O switches710 and 712 over transmit paths (not shown). In addition, although FIG.7 illustrates differential signals, embodiments of the present inventionare also applicable to single-ended signals.

In the blade server 700 of FIG. 7 (or a JBOD, SBOD or anybackplane/midplane system with dual paths), each of the redundant I/Oswitches A 710 and B 712 must have a priori information about which sloteach pair of transmission lines are going to, because the traces in themidplane 704 must have been designed in advance. In other words, uponcompletion of the design phase for the midplane 704, the transmissionline lengths are known for all connections between I/O switch A 710 andthe slots on the midplane, and for all connections between I/O switch B712 and the slots on the midplane. In one embodiment, both sets of pathlength information may be stored on an I/O switch in a memory device,which may include read-only memory, voltage dividers, or the like. Afterthe I/O switch is plugged into either the A or B side, then a redundantI/O switch location identifier such as a switch 758 may be used toidentify whether the I/O switch is plugged into the A or B side slot.Alternatively, the I/O switch may automatically identify its slotlocation after it is plugged into a slot by using a redundant I/O switchlocation identifier to read one or more slot location identificationpins in the connector, or the redundant I/O switch location identifiermay be a manually configured jumper which is installed before the I/Oswitch is inserted into a particular slot. Once the A or B sideinformation is known, the correct A or B side information can beretrieved, and each I/O circuit 754 in the I/O switch can know preciselythe path lengths that it is connected to. With this path lengthinformation, each I/O circuit 754 may set the pre-emphasis and orequalization for its driver 762 and receiver 764 accordingly.

On the other hand, because each server blade 702 can be plugged into anyslot on the midplane 704, the server blades 702 do not know where theirrespective transmission lines are going. However, it would be desirablefor the server blades 702 to identify the position or slot into which ithas been inserted, or know the path length for signals received from theI/O switches across the midplane 704. With this information, the serverblades 702 would be able to program optimized transmitter 782 andreceiver 778 settings (pre-emphasis and/or equalization) for the datalink.

To provide this path length information to the server blades 702 acrossthe midplane 704 without utilizing dedicated pins and/or connectors,each of the redundant I/O switches 710 and 712 contains a slotIDentification (ID) circuit 756 in each of the I/O circuits 754 employedfor facilitating communications between server blade slots in the bladeserver 700. Each I/O circuit 754 includes a driver 762 and receiver 764pair and a slot ID circuit 756 coupled to the driver signal paths. Theslot ID circuit 756 is fed by a slot voltage input 760, which providesan injected DC voltage representing the path length or slot number ofthe transmission line connecting the driver 762 to a slot on the otherside of the midplane 704.

The slot ID circuit 756 will send a DC voltage in common mode along theFC (or other high speed serial interface) transmission lines, allowingthe I/O switches to communicate path length or position or slot IDinformation to the server blades 702. In FIG. 7, I/O switch A 710generates an agreed upon DC voltage 760 in each I/O circuit 754 for eachof the paths it must communicate across, already knowing where thosepaths are routed. This may be accomplished using a Digital-to-Analog(D/A) converter, regulator, transistor, simple voltage divider, or thelike. This DC voltage 760 (chosen at the time of the design of thecircuit) corresponds to the information needed to be communicated. EachI/O circuit 754 may also communicate its own pre-emphasis and orequalization settings via the DC voltage value. The DC slot voltage 760is first filtered via low pass filter 766 to remove any frequency(noise) components that might interfere with the desired datatransmission, and is then coupled into the transmission lines 770 viahigh impedance elements 768. Elements 768 may be simply resistors, RadioFrequency (RF) chokes, bias T's, or any device capable of coupling in aDC voltage while having sufficiently high impedance at the desired datafrequencies so as not to disturb the data communication. Thetransmission lines 770 must be DC blocked at 772 (typically using acoupling capacitor) in order to keep the common mode voltage frominterfering with driver 762.

In the example of FIG. 7, one I/O circuit 754 in I/O switch A 710coupled to slot 3 is shown, and one I/O circuit in I/O switch B 712coupled to slot 3 is shown, for purposes of illustrating the alternativeembodiment. The driver outputs from these I/O circuits travel theshorter path 716 and the longer path 718 and enter the mezzanine I/Ocard 714 on the server blade 702, where they are routed to a receivingcircuit, typically a SERDES 720.

The injected common mode DC voltage is again DC blocked at 776 in orderto prevent the DC voltage from interfering with receiver 778. Near theSERDES 720 the transmission lines 716 and 718 are sampled differentiallyby high impedance elements 726. These high impedance elements 726 arehigh enough impedance as compared to the impedance of the transmissionlines 716 and 718 (on the order of 10× or more) so as to sample the datastream, but not disturb the data being received. The sampled injected DCvoltage is then low pass filtered by filter 774 and converted to adigital value by A/D converter 780 with the path length determinationcircuit 788. Note that A/D converter 780 could also be implemented in awindow comparator. Once the hardware 722 and/or processor 724 within thepath length determination circuit 788 receives the digital value, it candetermine the path length and how much pre-emphasis and or equalizationis needed on its side of the link. Hardware 722 and/or processor 724 canthen independently program the drivers 778 and/or receivers 782 of eachSERDES 720 with the appropriate values via control signals 784 and 786,respectively, to equalize the path losses and provide minimum bit errorrate across its links.

The slot identification circuitry in the server blade 702 according toalternative embodiments of the present invention is shown surroundingthe SERDES 720 in the example of FIG. 7. However, it should beunderstood that although the slot identification circuitry is shown inFIG. 7 within the mezzanine I/O card 714, it may be located in otherlocations on the server blade 702 or receiving device.

Although the present invention has been fully described in connectionwith embodiments thereof with reference to the accompanying drawings, itis to be noted that various changes and modifications will becomeapparent to those skilled in the art. Such changes and modifications areto be understood as being included within the scope of the presentinvention as defined by the appended claims.

1. An apparatus in a receiving device for generating path lengthinformation for first and second receive paths, comprising: first andsecond filters coupled to the first and second receive paths forreceiving communication signals and providing first and second filteroutputs passing only those communication signals within a frequencyrange of interest and having first and second voltage/frequencycharacteristics representative of a length of the first and secondreceive paths; and a path length determination circuit coupled to thefirst and second filter outputs for generating first and second receivepath length information from the first and second voltage/frequencycharacteristics.
 2. The apparatus as recited in claim 1, the first andsecond receive path length information including an identification of alonger and shorter of the first and second receive paths, the first andsecond voltage/frequency characteristics being peak values of anamplitude of the communication signals within the frequency range ofinterest, the path length determination circuit comprising: first andsecond envelope detectors coupled to the first and second filter outputsfor generating DC voltages representative of the peak values of thecommunication signals on the first and second receive paths within thefrequency range of interest; and a first comparator coupled to each ofthe envelope detectors for receiving the DC voltages and indicatingwhich of the first and second receive paths are the longer and shorterreceive paths.
 3. The apparatus as recited in claim 2, furthercomprising: one or more first and second high impedance elements coupledto each of the first and second receive paths for sensing thecommunication signals on each of the first and second receive paths; andfirst and second amplifiers coupled between the one or more first andsecond high impedance elements and the first and second filters in eachof the first and second receive paths for boosting the sensed signals.4. The apparatus as recited in claim 3, the first and second receivepath length information including a magnitude of a difference betweenthe longer and shorter of the first and second receive paths, the pathlength determination circuit further comprising a differential amplifiercoupled to each of the first and second envelope detectors forgenerating a voltage representative of the magnitude of the differencebetween the longer and shorter of the first and second receive paths. 5.The apparatus as recited in claim 4, further comprising a secondcomparator coupled to the differential amplifier and a thresholdreference voltage for indicating a location of the receiving device. 6.The apparatus as recited in claim 2, wherein the frequency range ofinterest includes those frequencies at which the longer of the first andsecond receive paths has significant loss as compared to the shorter ofthe first and second receive paths.
 7. The apparatus as recited in claim2, wherein the frequency range of interest includes the highestfrequencies possible for a communication protocol being utilized overthe first and second receive paths.
 8. The apparatus as recited in claim2, further comprising: first and second receivers coupled to each of thefirst and second receive paths; and first and second equalizationcircuits within the first and second receivers for adjusting a frequencyresponse of the first and second receive paths; wherein the path lengthdetermination circuit further comprises a first Analog to Digital (A/D)converter coupled to the first comparator for converting the indicationof which of the first and second receive paths are the longer andshorter paths into a first digital value, and a circuit coupled betweenthe first A/D converter and the first and second equalization circuitsfor controlling the first and second equalization circuits to flattenout the frequency response of each of the first and second receive pathsin accordance with the first digital value.
 9. The apparatus as recitedin claim 4, further comprising: first and second receivers coupled toeach of the first and second receive paths; and first and secondequalization circuits within the first and second receivers foradjusting a frequency response of the first and second receive paths;wherein the path length determination circuit further comprises a firstAnalog to Digital (A/D) converter coupled to the first comparator forconverting the indication of which of the first and second receive pathsare the longer and shorter paths into a first digital value, a secondA/D converter coupled to the differential amplifier for converting themagnitude of the difference between the longer and shorter of the firstand second receive paths into a second digital value, and a circuitcoupled between the first and second A/D converters and the first andsecond equalization circuits for controlling the first and secondequalization circuits to flatten out the frequency response of each ofthe first and second receive paths in accordance with the first andsecond digital values.
 10. The apparatus as recited in claim 5, furthercomprising: first and second receivers coupled to each of the first andsecond receive paths; and first and second equalization circuits withinthe first and second receivers for adjusting a frequency response of thefirst and second receive paths; wherein the path length determinationcircuit further comprises a first Analog to Digital (A/D) convertercoupled to the first comparator for converting the indication of whichof the first and second receive paths are the longer and shorter pathsinto a first digital value, a second A/D converter coupled to the secondcomparator for converting the indication of the location of thereceiving device into a second digital value, and a circuit coupledbetween the first and second A/D converters and the first and secondequalization circuits for controlling the first and second equalizationcircuits to flatten out the frequency response of each of the first andsecond receive paths in accordance with the first and second digitalvalues.
 11. A mezzanine I/O card comprising the apparatus of claim 2.12. A server blade comprising the mezzanine I/O card of claim
 11. 13. Ablade server comprising the server blade of claim
 12. 14. A Storage AreaNetwork (SAN) comprising the blade server of claim
 13. 15. The apparatusas recited in claim 1, wherein the path length determination circuitfurther comprises circuitry utilizing the first and second receive pathlength information to set equalization or pre-emphasis in a receiver ora transmitter.
 16. A method for generating path length information in areceiving device for first and second receive paths, comprising:filtering each of the first and second receive paths and passing onlythose communication signals within a frequency range of interest andhaving first and second voltage/frequency characteristics representativeof a length of the first and second receive paths; and generating firstand second receive path length information from the first and secondvoltage/frequency characteristics.
 17. The method as recited in claim16, the first and second receive path length information including anidentification of a longer and shorter of the first and second receivepaths, the first and second voltage/frequency characteristics being peakvalues of an amplitude of the communication signals within the frequencyrange of interest, the method further comprising: performing envelopedetection on the filtered first and second receive paths and generatingDC voltages representative of the peak values of the communicationsignals on the first and second receive paths within the frequency rangeof interest; and comparing the generated DC voltages and indicatingwhich of the first and second receive paths are the longer and shorterreceive paths.
 18. The method as recited in claim 17, furthercomprising: sensing the communication signals on each of the first andsecond receive paths in a non-disruptive manner; and amplifying thesensed signals in each of the receive paths prior to filtering.
 19. Themethod as recited in claim 17, the first and second receive path lengthinformation including a magnitude of a difference between the longer andshorter of the first and second receive paths, the method furthercomprising differentially amplifying each of the generated DC voltagesfor generating a voltage representative of a magnitude of a differencebetween the longer and shorter of the first and second receive paths.20. The method as recited in claim 18, further comprising comparing thevoltage representative of the magnitude of the difference between thelonger and shorter of the first and second receive paths and a thresholdreference voltage for indicating a location of the receiving device. 21.The method as recited in claim 17, wherein the frequency range ofinterest includes those frequencies at which the longer of the first andsecond receive paths has significant loss as compared to the shorter ofthe first and second inband receive paths.
 22. The method as recited inclaim 17, wherein the frequency range of interest includes the highestfrequencies possible for a communication protocol being utilized overthe first and second receive paths.
 23. The method as recited in claim17, further comprising: converting the indication of which of the firstand second receive paths are the longer and shorter paths into a firstdigital value; and equalizing a frequency response of each of the firstand second receive paths in accordance with the first digital value. 24.The method as recited in claim 19, further comprising: converting theindication of which of the first and second receive paths are the longerand shorter paths into a first digital value; converting the magnitudeof the difference between the longer and shorter of the first and secondreceive paths into a second digital value; and equalizing a frequencyresponse of each of the first and second receive paths in accordancewith the first and second digital values.
 25. The method as recited inclaim 20, further comprising: converting the indication of which of thefirst and second receive paths are the longer and shorter paths into afirst digital value; converting the indication of the location of thereceiving device into a second digital value; and equalizing a frequencyresponse of each of the first and second receive paths in accordancewith the first and second digital values.
 26. The method as recited inclaim 16, further comprising: utilizing the first and second receivepath length information to set equalization or pre-emphasis in areceiver or a transmitter.